# Markov mode-multiplexing mode in OFDM outphasing transmitters

## Abstract

Outphasing transmitters have been explored to study the trade-off between linearity and efficiency. The outphasing technique enhances efficiency by operating two amplifiers at lower output amplitudes, using two constant envelope signals. Their major drawback is the inherent sensitivity to gain and phase imbalances between the two amplifier branches. Another important issue is related to the degradation of efficiency, especially in isolated combiners. This paper presents a Statistical Markov-Chain Mode-Multiplexing (MM) transmitter which combines features of the MM and Reverse MM-LINC. Commercial analog devices and a digital platform for signal processing purposes are used to test the performance with an orthogonal frequency multiplexing modulation (OFDM), which is one of the most used modulation schemes in wireless communication systems.

## Keywords

PAPR OFDM Outphasing## Abbreviations

- ACPR
Adjacent channel power ratio

- ADC
Analog digital converter

- DAC
Digital analog converter

- DSP
Digital signal processor

- EER
Envelope elimination and restoration

- FBMC
Filtered band multicarrier

- FPGA
Field programmable gate array

- GFDM
Generalized frequency division multiplexing

- LINC
Linear amplification with non-linear components

- LTE
Long-term evolution

- MILC
Modified implementation of LINC

- MM-LINC
Mode-multiplexing LINC

- OFDM
Orthogonal frequency multiplexing modulation

- PA
Power amplifier

- PAPR
Peak-to-average power ratio

- PC
Personal computer

Probability density function

- QPSK
Quadrature phase-shift keying

- RAM
Random access memory

- RF
Randiofrequency

- RM-LINC
Reverse mode LINC

- ROM
Read-only memory

- SCS
Signal component separator

## 1 Introduction

Radio frequency power amplifiers (PAs) are the most critical components in the design of spectral and power efficient wireless transmitters. Many transmitted signals in the new standards, such as long-term evolution (LTE), and the future 5G multicarrier-based modulation schemes such as Filtered Band Multicarrier (FBMC) and Generalized Frequency Division Multiplexing (GFDM) have a high peak-to-average power ratio (PAPR) caused by complex modulation schemes. The use of high PAPR signals requires a large enough back-off in the power amplifier operating to satisfy the stringent linearity requirement, but this region shows a very low PA efficiency. Recent trends in efficient and linear PA research are mainly focusing on the use of two-branch amplifier systems and moving away from the classical single-ended amplifier topology combined with the use of digital predistortion techniques. Among these dual-branch systems, the most popular are the Doherty amplifier, the envelope elimination and restoration (EER) techniques, the linear amplification with nonlinear components (LINC), and the modified implementation of the LINC (MILC technique) [1, 2, 3].

This paper presents a complete design and experimental implementation of a new Mode-Multiplexing LINC technique [4, 5] in order to enhance the efficiency with a reduced spectral regrowth. The paper is outlined as follows. In Section 2, we introduce the previous mode multiplexing methods applied in the context of the LINC. The novel Markov mode multiplexing method is explained in Section 3. The simulations, which have been accomplished to analyze the proposed technique, are shown in Section 4. The proposed algorithm is validated by means of an experimental setup and the main results are discussed in Section 5. Finally, some conclusions about this work are provided in Section 6.

## 2 Mode-multiplexed LINC methods

There are some issues which decrease the overall performance in a LINC transmitter implementation, namely the power gain and phase imbalance between the two RF paths. These are typically due to PAs, mixers, path length differences, quadrature modulators errors, quantization noise, and sampling rate error [6, 7, 8, 9]. A LINC scheme which is implemented with an isolated combiner shows an efficiency which is the product of those corresponding to both PA and combiner [2, 10, 11]. Although PA efficiency is maximized, the whole performance is dramatically reduced in a LINC structure if the combiner efficiency is taken into account. Therefore, some techniques, like the Mode-Multiplexing method (MM-LINC), have been proposed either to improve combiner efficiency or linearity (Reverse Mode, RM-LINC) [4].

*s*(

*n*) (we use \(s(n)=s(t)|_{t=n\cdot T_{m}}\), being

*T*

_{ m }the sampling period to describe its discrete version) is split into two constant envelope signals of a LINC transmitter by a Signal Component Separator block (SCS).

*j*

*e*(

*n*) is a signal which is in quadrature to the source signal,

*s*(

*n*)=

*c*(

*n*)

*e*

^{jρ(n)}, and it is evaluated as

*c*

_{max}is the maximum of the signal envelope

*c*(

*n*). If the LINC decomposition is expressed in matrix form,

*Θ*by

The MM-LINC switches between the so-called outphasing (constant envelope, here denoted by “O”) and balanced modes (original envelope with 3-dB backoff, denoted by “B”), shown in Fig. 1 as a state diagram. The MM-LINC decomposition improves the LINC transmitter efficiency because the outphasing angle is reduced compared to the standard LINC solution. The reverse mode is obtained by inverting the inequalities in (4), achieving a better linearization instead of an efficiency improvement. The threshold *γ* must be optimized for every desired transmitted waveform, and thus, the method performance depends on the signal probability density function. Authors propose a novel switching method (Markov mode-multiplexing) which allows to transmit any particular envelope value in certain time step as outphasing mode but as a balanced mode later.

## 3 Markov chain MM-LINC technique

### 3.1 Algorithm principles

*Λ*matrix is driven through a Markov chain and is defined as

where *π*(*n*) is the Markov state. The sequence of binary-valued random samples *π*(0),*π*(1),…*π*(*n*) can be easily generated in a digital platform (DSP or FPGA) or can be offline created and stored in a RAM or ROM if desired to reduce the computational cost [12]. In addition, it should fulfill the so-called Markov property [13], and each binary value, i.e., the state value, controls the transmitting mode (“OUTPHASING (O)”, “BALANCED (B)”).

where *α* is a binary sequence which controls the statistical properties of the PA input signals, and consequently the trade-off between efficiency and linearity. The MM-LINC sequence is based on the input samples (“1,” if the instantaneous envelope is greater than the threshold, “0” otherwise), and in our proposal, it is based on the mathematical properties of a Markov process.

*a*and

*b*are values specified by the designer. These are the probabilities of going from state BALANCED to OUTPHASING (or the opposite), in one time step. Besides, the sum of all the probabilities leaving a state must be one. Under this lossless chain assumption, the random state is modeled with the aid of a transition probability matrix which is given by

Furthermore, we study two magnitudes so that the effects of *a* and *b* can be investigated and the operative principles can be properly understood:

**(i) Percentage of outphasing or balanced samples:**the greater the number of LINC-transmitted samples, the higher the PA efficiency and the lower the isolated combiner efficiency. Those are estimated by means of the steady state probabilities, which are computed using (9) and

where *P*_{ O } is the probability of a sample of being transmitted in outphasing mode and *P*_{ B } of the balanced mode.

**(ii) The averaged time of being in outphasing (balanced) mode before changing to balanced (outphasing) mode:**This property is related to how many samples are consecutively transmitted in the same mode (neglecting instantaneous envelope values). It quantifies the correlation properties of the signal and the switching rate between modes. According to Markov chain theory, the number of average samples for each state (

*N*

_{ O },

*N*

_{ B }) is computed as

The importance of these equations will be addressed with the simulations and with analysis of the theoretical PAPR. Theory and results will be focused on OFDM-like modulations due to the widespread use in actual wireless communication systems, but the technique is applicable to other modulation formats such as WCDMA. Markov LINC reduces the PAPR of the decomposed signal in comparison to the mode multiplexing method, and consequently, there will be a noticeable difference between both with high PAPR waveforms.

### 3.2 PAPR theorical performance

*s*

_{ n }is defined as [14, 15]

*E*[|

*s*

_{ n }|

^{2}] is its averaged power. As far as a generic OFDM signal is concerned, it is assumed that the asymptotic probability distribution (pdf) follows a Rayleigh statistics since the inphase and quadrature components approximate to Gaussian processes,

being *σ* the inphase or quadrature variance.

*c*

_{max}/2 as

being *δ* the Dirac distribution. Notice that in the case of the classical LINC, PAPR=1.

#### 3.2.1 MM-LINC PAPR

*γ*threshold. Thus, the probability distribution is computed in the balanced mode by constraining the envelope distribution to

*γ*, which leads to

*u*(

*x*) the Heaviside function. Finally, it is important to realize that the envelope is transmitted in the balanced mode with a 3 dB backoff. Using (15), (18), and (20) and a change of variable, it is found that

*γ*is properly selected, the numerator in (14) comes from the LINC constant envelope property, which yields to

#### 3.2.2 Markov-multiplexed LINC PAPR

*c*

_{max}/2 instead of

*γ*, which is usually less than

*c*

_{max}/2. This stems from the fact that the switching policy is precisely independent from the signal amplitude and consequently

The PAPR Eqs. (25) and (29) may forecast suitable values for *γ* and the relation *a*/*b* in order to fix a specified PAPR after estimating the input original OFDM signal statistical moments. Two practical waveforms test the proposed equation validity in this work, a QPSK OFDM downlink signal with 1.4 and 5 MHz bandwidth. The decomposition process is accomplished by means of the Matlab platform.

*γ*), and the steady-state probability

*τ*=

*P*

_{ B }. According to Fig. 3a, both methods can achieve PAPR values between 0 dB (fully LINC mode) and the PAPR of the original signal. However, the Markov decomposed signal PAPR is lower for a wider range of

*a*and

*b*values and increases quickly when

*τ*approaches the complete balanced state. As expected, both policies agree in the limiting cases (LINC and balanced limits).

*γ*=

*E*[(|

*s*(

*n*)|] and

*a*=

*b*=0.01). The prediction (Table 2) agrees with those numerically calculated, but there is a small difference in the Markov case. This is due to fact that the estimated value is a single realization of the process, whereas (29) computes averaged values.

Input envelope statistical values and PAPR

Bandwidth | | E[ |
| PAPR (dB) |
---|---|---|---|---|

1.4 MHz | 0.1096 | 0.01974 | 1.19·10 | 13.73 |

5 MHz | 0.1654 | 0.04019 | 5.93·10 | 10.93 |

Multiplexing-Mode LINC theoretical and real PAPR values

Bandwidth | Policy | Real PAPR (dB) | Pred. PAPR (dB) |
---|---|---|---|

1.4 MHz | Reverse MM | 3.3487 | 3.2575 |

Markov | 2.9479 | 2.83018 | |

5 MHz | Reverse MM | 3.369 | 3.3111 |

Markov | 2.95 | 2.6734 |

Figure 3b shows the probability density functions not only of the OFDM signal envelopes, which are well approximated using the Rayleigh distribution, but also of the classical multiplexing mode and the Markov mode envelopes. Their pdfs have strong peaks in the *c*_{max}/2 envelope value, which are clearly outphased LINC samples. According to Fig. 3b, there are strong differences in the balance mode statistics which leads to different performance in terms of efficiency and linearity.

## 4 Simulation Analysis

The importance of the Markov chain parameters *a* and *b* has been shown in previous sections. On the one hand, PAPR can be selected according to the percentage of outphased signal samples. On the other hand, this allows us to properly set the ratio *a*/*b* but not to fix numerical values for *a* and *b*. Distortion analysis can be helpful in order to finally choose suitable values which aim at obtaining good performance in terms of linearity and efficiency. Markov LINC simulations are carried out to study the performance and to compare to the MM-LINC and classical LINC. Firstly, a PA model is extracted from real measurements using a polynomial model (PM) with an OFDM signal source. Secondly, an ACPR analysis is addressed using the PA models to draw some conclusions about *a* and *b* independently. Finally, the LINC structure is evaluated in an ideal scenario (both branches do not have imbalances).

*x*(

*t*),

*y*(

*t*) respectively,

*ϕ*

_{ p }is a basis function with terms in the form of |

*x*(

*t*)|

^{ p }

*x*(

*t*),

*α*

_{ p }are complex coefficients,

*N*is the nonlineary order, the PM:

In this work, the real modeled PA is the CREE CGH40006P, which has 1-dB compression around 29.9 dBm and is measured around 2.6 GHz using multicarrier modulation with two different signal bandwidths, 1.4 and 5 MHz. Finally, the PM model has been trained up to order 7.

Transition probabilities are the key parameters which may be analyzed to minimize spectral regrowth. Some Monte Carlo simulations have been carried out to study their effects on ACPR and efficiency. Figures 4b and 5b show that better efficiencies are achieved when the transition probabilities *a* and *b* are relatively close. Intuitively, if combiner and PA efficiencies would increase/decrease at the same rate, then a 50% would be the optimal value in terms of efficiency and distortion. The efficiency rate depends on the bias of the PAs and is different from that of the combiner. Thus, the trade-off solution is not exactly at this point but close. As a conclusion, some optimization algorithm should be carried to choose the accurate proportion between outphasing and balanced samples in order to fulfill a standard specification.

In addition, the higher values of transition probabilities, the faster the modes switch (*N*_{ B },*N*_{ O }, are smaller) due to the time variability of the signals. The Markov sequence multiplies the samples, and *a* and *b* must fulfill the sampling theorem. Therefore, the signal bandwidth plays an important role so that the transition probabilities do not cause aliasing in the signal component separation process.

*γ*=0.18,

*a*=

*b*=0.01) just to check if the proposed technique works. These values have been chosen so that the output power with both multiplexing schemes were similar in order to have an efficiency which is comparable. Alternatively, those values could have been chosen to provide similar ACPR and then verify if the Markov technique provides better efficiency. Nevertheless, a proper optimization algorithm should be investigated or a utility function should be defined in order to choose the best trade-off according to the needs and requirements of a specific wireless scenario.

As expected, the Markov MM-LINC outperforms the standard mode multiplexing method because its signals have a better PAPR, leading to identical output power but less adjacent channel interference.

Estimated efficiency bounds (%) OFDM 1 MHz bandwidth

Conf. | Class A | Class B | Comb. | Total A | Total B |
---|---|---|---|---|---|

LINC | 25 | 39.27 | 4.23 | 1.06 | 1.66 |

MMLINC | 12.87 | 20.21 | 57.98 | 7.45 | 11.72 |

Markov | 14.36 | 22.56 | 53.84 | 7.73 | 12.15 |

Estimated efficiency bounds (%) OFDM 5 MHz bandwidth

Conf | Class A | Class B | Comb. | Total A | Total B |
---|---|---|---|---|---|

LINC | 25 | 39.27 | 8.07 | 2.02 | 3.17 |

MMLINC | 13.07 | 20.53 | 62.03 | 8.11 | 12.73 |

Markov | 16.55 | 26 | 49.75 | 8.23 | 12.93 |

## 5 Experimental evaluation

### 5.1 Implementation

Three mode-multiplexing algorithms have been tested on a LINC prototype to verify the real improvement and to find out if the trends predicted through simulations are accurate.

*k*

_{ i }and phase

*ϕ*

_{ i }of the outphasing signals

*s*

_{1}(

*n*) and

*s*

_{2}(

*n*) through two complex coefficients

*f*of the correction coefficients,

where *y*(*n*) is an attenuated version at the combiner output. Once they are compensated, the signals corresponding to the different signal separation component methods are transmitted.

It must be pointed out that simulations do not include either memory effects or imbalances in the whole RF chain; hence, simulated and experimental figures are not directly comparable. Simulations are used in this case for designing the algorithms and the real setup is used for confirming the proposed approach.

*P*

_{DC}) and output power (

*P*

_{out}), which are measured using the power supply and a spectrum analyzer (EXA N9010A). The total LINC efficiency (PA and combiner) can be evaluated as

takes into account the improvement or degradation in efficiency.

### 5.2 Results

Experimental LINC and mode-multiplexing results BW = 1.4 MHz

BW = 1.4 MHZ | Pout (dBm) | ACPR (dBc) | | | Eff % | FoM | EVM % |
---|---|---|---|---|---|---|---|

LINC | 26.3 | 29.3 | 13.32 | 12.35 | 1.66 | 1 | 2.47 |

MM-LINC | 27.1 | 18.9 | 7.84 | 7.5 | 3.34 | 2.01 | 4.1 |

Markov | 29.1 | 30.3 | 10.33 | 9.07 | 4.16 | 2.51 | 8.7 |

Experimental LINC and mode-multiplexing results BW = 5 MHz

BW = 5 MHz | Pout (dBm) | ACPR (dBc) | | | Eff % | FoM | EVM % |
---|---|---|---|---|---|---|---|

LINC | 28.1 | 31.9 | 11.12 | 11.48 | 2.86 | 1 | 7.05 |

MM-LINC | 28.3 | 31.4 | 6.44 | 6.92 | 5.06 | 1.77 | 9.28 |

Markov | 29.2 | 34.8 | 7.84 | 7.7 | 7.7 | 1.87 | 11.16 |

Although impairments are not studied in simulations, experimental results show their effects on the 5 MHz OFDM signal. It should require a more robust memory mismatch correction algorithm to improve out-of-band cancellation, and in contrast, Markov MM-LINC waveforms seem to be less sensitive to RF chain imbalances, as the ACPR is better than in the standard LINC. The Markov-outphased signals do not have such a great signal bandwidth compared to the LINC signals, and therefore, impairments due to memory effects are small in comparison with the standard LINC and easier out-of band cancellation can be carried out. To sum up, the proposed method can comparatively achieve similar results than the MM-LINC method but with better ACPR, which is one of the characteristics of the reverse MM-LINC.

## 6 Conclusion

In this work, a novel mode multiplexing method for LINC transmitters is presented, implemented, and verified. A mathematical analysis of the PAPR proves that the new policy behaves better in terms of spectral regrowth compared to other proposed multiplexing policies, which has been verified by means of simulation. The experimental LINC transmitter has been implemented and tested with OFDM signals, obtaining good performance with low complexity. Experimental results demonstrate that it is possible to reduce the ACPR up to 4.5 dB in a system with a multicarrier modulation without decreasing the output mean power, compared to standard MM methods, and improving efficiency by approximately 2 compared to the classical LINC technique.

## 7 \thelikesection Appendix

## Notes

## Funding

This work was supported by the spanish Government (Project TEC2014-58341-C4-2-R from MICINN and FEDER) and the Aragón Government and FSE (GCM T97).

### Authors’ contributions

PLC contributed to the measurements, result analysis, and article writing. PG-D contributed to the result analysis and article writing. JdeM contributed to the result analysis and article writing. AV contributed to the article writing. All authors read and approved the final manuscript.

## Competing interests

The authors declare that they have no competing interests.

## Publisher’s Note

Springer Nature remains neutral with regard to jurisdictional claims in published maps and institutional affiliations.

## References

- 1.PM Lavrador, TR Cunha, PM Cabral, JC Pedro, The linearity efficiency compromise. IEEE Microw. Mag.
**11**(5), 44–58 (2010).CrossRefGoogle Scholar - 2.A Birafane, M El-Asmar, AB Kouki, M Helaoui, FM Ghannouchy, Analyzing LINC systems. IEEE Microw. Mag.
**11**(5), 59–71 (2010).CrossRefGoogle Scholar - 3.B Kim, J Moon, I Kim, Efficiently Amplified. IEEE Microw. Mag.
**11**(5), 87–99 (2010).CrossRefGoogle Scholar - 4.M Helaoui, FM Ghannouchi, Linearization of power amplifiers using the reverse MM-LINC technique. IEEE Trans. Circuits Syst. II, Exp. Briefs.
**57**(1), 6–10 (2010).CrossRefGoogle Scholar - 5.M Helaoui, S Boumaiza, FM Ghannouchi, AB Kouki, A Ghazel, A new mode-multiplexing LINC architecture to boost the efficiency of WiMAX up-link transmitters. IEEE Trans. Microw. Theory Techniques.
**55**(2), 248–253 (2007).CrossRefGoogle Scholar - 6.P Garcia-Ducar, A Ortega, J de Mingo, A Valdovinos, Nonlinear distortion cancellation using LINC transmitters in OFDM system. IEEE Trans. Broadcast.
**51**(1), 84–93 (2005).CrossRefGoogle Scholar - 7.P Garcia-Ducar, J de Mingo, PL Carro, A Valdovinos, Design and experimental evaluation of a LINC transmitter for OFDM systems. IEEE Trans. Wirel. Commun.
**9**(10), 2983–2987 (2010).CrossRefGoogle Scholar - 8.T Hwanq, K Azadet, RS Wilson, J Lin, Linearization and imbalance correction techniques for broadband outphasing power amplifiers. IEEE Trans. Microw. Theory Tech.
**63**(7), 248–253 (2015).Google Scholar - 9.AF Aref, TM Hone, R Negra, A study of the impact of delay mismatch on linearity of outphasing transmitters. IEEE Trans. Circ. Syst. I.
**62**(1), 254–262 (2015).Google Scholar - 10.FH Raab, Efficiency of outphasing RF power-amplifier systems. IEEE Trans. Commun.
**33**(10), 1094–1099 (1985).CrossRefGoogle Scholar - 11.T Hwanq, K Azadet, RS Wilson, J Lin, On the linearity and efficiency of outphasing microwave amplifiers. IEEE Trans. Microw. Theory Tech.
**52**(7), 1702–1708 (2004).CrossRefGoogle Scholar - 12.PL Gilabert, A Cesari, G Montoro, E Bertrand, J Dilhac, Multi-lookup table FPGA implementation of an adaptive digital predistorter for linearizing RF power amplifiers with memory effects. IEEE Trans. Microw. Theory Tech.
**56**(2), 372–384 (2008).CrossRefGoogle Scholar - 13.H Yang, M Alouini, Markov chains and performance comparison of switched diversity systems. IEEE Trans. Commun.
**52**(7), 1113–1125 (2004).CrossRefGoogle Scholar - 14.H Ochiai, H imai, On the distribution of the peak-to-average power ratio in OFDM signals. IEEE Trans. Commun.
**49**(2), 282–289 (2001).CrossRefMATHGoogle Scholar - 15.H Ochiai, An analysis of band-limited communication systems from amplifier efficiency and distortion perspective. IEEE Trans. Commun.
**61**(4), 282–289 (2013).CrossRefGoogle Scholar - 16.DR Morgan, Z Ma, J Kim, MG Zierdt, J Pastalan, A generalized memory polynomial model for digital predistortion of RF power amplifiers. IEEE Trans. Microw. Theory Tech.
**54**(10), 3852–3860 (2006).MATHGoogle Scholar - 17.K Hyunchul, JS Kenney, Behavioral modeling of nonlinear RF power amplifiers considering memory effects. IEEE Trans. Microw. Theory Tech.
**51**(12), 2495–2504 (2003).CrossRefGoogle Scholar - 18.W Huadong, B Jingfu, W Zhengdu, Comparison of the behavioral modelings for RF power amplifier with memory effects. IEEE Microw. Wireless Components Lett.
**19**(3), 179–181 (2009).CrossRefGoogle Scholar

## Copyright information

**Open Access** This article is distributed under the terms of the Creative Commons Attribution 4.0 International License (http://creativecommons.org/licenses/by/4.0/), which permits unrestricted use, distribution, and reproduction in any medium, provided you give appropriate credit to the original author(s) and the source, provide a link to the Creative Commons license, and indicate if changes were made.